Timing Improvements to Silicon Photomultiplier Transimpedance Amplifier Circuit

Question

I'm designing another Silicon Photomultiplier circuit. Right now, it is in the theoretical stage. My team and I have made numerous circuits, and the basic template is below:

^{simulate this circuit – Schematic created using CircuitLab}

Below are some links to the main parts used:

https://www.digikey.com/product-detail/en/texas-instruments/OPA656N-250/OPA656N-250CT-ND/431967

http://sensl.com/estore/microfj-60035-tsv/

The amplifier is the Texas Instruments OPA656 op amp. It contains a slew rate of 295 V/µs and a bandwidth of 500 MHz.

The Silicon Photomultiplier (SiPM) is a SensL MicroFJ-60035-TSV, the 6 mm version. It contains a PDE of 51%, and it has a gain of 5.3*10^6 from the anode to the cathode, and a typical dark current of 4.1 µA, with a rise time of 300 ps, and a max current limit of 15 mA.

The resistors and capacitors can be adjusted as needed, but this is what my team is working with so far. We have two channels, each independent of each other in this configuration, and the team is trying to measure coincidences between the two. Now, my training is as an electrical engineer, not a nuclear engineer, so this is all new to me, but from what the team has told me briefly, between measuring the time between the two detectors, we are getting around 400 ps. Now, I'm not sure if this is the time difference between the two channels or if this is the rise time of one individual channel, but when I find out more information, I will update this accordingly.

The timing is good, but because the amplitude was smaller than what we require, we had to use an external amplifier to 'boost' the signal. From what I was told, the external amplifier did not affect the timing, but we can't rely on it forever. Thus, I was wondering what I could do to improve the timing of this circuit while achieving a larger amplitude? We are hoping to try and achieve a coincidence timing of 300 ps.

The amplitude can be adjusted by adjusting R1 and C1, so I'm not entirely concerned about that. The one thing that I don't really know how to adjust is the speed. My first thought was to switch out the OPA656 for another amplifier with a faster slew rate, but it feels like just swapping it out might not be enough. Obviously, there are other considerations to take into account when picking a new amplifier, but how can I pick a better one taking into account the parameters of the op amp? If we're talking about just the schematic below, putting aside the board layout for now, what else can I do for the timing?

EDIT: My team gave me some values for what they want out of this circuit, so I added them below, and I also adjusted the circuit to showcase the current board schematic. I apologize for not making it clearer, but with the current comments they gave me, I felt it was imperative that I highlight the change.

Currently, our board uses a single set of power supplies (-30 V, +5V, -5V, and GND) to power the entire board. This is shared amongst all SiPMs and op-amps with just one set of decoupling capacitors. For the next design, I'll make sure to power them independently of each other.

We achieved a signal rise time of 6.5 to 9 ns using a 25 ohm resistor. Initially, our feedback resistor was 470 ohms, and while that provided a high gain, it was too slow for our needs. We played around with various feedback resistor values, and we found that 25 ohms gave a really fast time. However, the issue with this value is that the gain is very low, with the max amplitude being around 160 mV, so we needed a second amplification which was done through a NIM module. For my next design, we would like to keep the timing as low as possible while hopefully achieving a 600-850 mV output voltage, a rough gain of 5.5x, so that we can take advantage of the dynamic range of our ADCs. What would be the best way to go about this, keeping the speed the same while increasing gain? Assuming that we power each channel independently in the future, the only other major change I can think of is swapping out the op-amp for another one with faster slew rate and step time.

Answer 1

Don't share the -30V reference for both channels. Instead, duplicate R3 R4 C6 C7 for each channel, this will lower crosstalk.

If you want to measure the delay between both pulses, then both circuits should have identical delays. Since you're down into picoseconds, propagation delay in traces matters. Since FR-4 propagation time varies slightly with temperature, I'd advise having two absolutely identical layouts, with very short traces to the coax connectors.

This will need to be validated by feeding the same pulse of light via matched length fiber optics into the sensors, then checking the delay between recorded pulses. They should be identical. After this, swap the fibers and measure again. Or shine a very fast laser on both sensors simultaneously. Anyway, you get the idea: circuit performance must be validated.

I'm gonna disagree with analogsystemsrf on decoupling: since the inductance of the bondwires inside your opamp is higher than the inductance of a single, well-routed SMD cap, the number of decoupling caps doesn't matter. What matters is that the decoupling cap should be as close as possible to the chip. It should also be large enough to provide all the current needed during the event.

I'd put a 1µF 0805 cap as close as possible, then connect this to the main supply via a 1R resistor. The main supply should have a local cap, like 10µF MLCC.

If you hand solder it, you can stick the decoupling cap really close, closer than pick&place clearances would allow.

Use the SOT23 package, it will have lower inductance.

What would be the best way to go about this, keeping the speed the same while increasing gain?

You could use a faster opamp like LMH6629 OPA847 ADA4895 but of course these are even more finicky about layout.

Must-read links:

http://www.eetimes.com/document.asp?doc_id=1274887

http://mksa.dii.univpm.it/biblioteca/sala_tecnica/scaffale_dispositivi/instr_amp/AN-202.pdf

Answer 2

There are a few things that you have to separate here. Timing precision, timing accuracy and rise/fall time. Timing precision tells you how repeatable your timing is over multiple measurements, or how stable it is. Accuracy is about how accurately the timing (delay) through the circuit is defined. And the rise time tells you how fast the signal at the output rises. If I understood you correctly, you are doing difference measurements between the two channels, thus accuracy is not important, as long as the two channels behave the same. Rise/fall time is probably also not important, unless you have high repetition rates. So the only thing you should really care about is timing precision.

That said, 400ps is not that hard, but you are already in the sub-ns region, where all kinds of weird effects pop up. First of all, you have to ensure that noise is kept low. And this also includes the 1/f^a noise (flicker noise and other higher exponent power law noise). In this case, you want the photodiodes to be the limiting elements in the circuit. One general design principle when doing circuits with high timing precision is, that you have to treat your circuit like it was an RF circuit. Ie. if you are after 1ns precision, design it like you are handling a 1GHz signal. Keep it well shielded, in properly specified impedance transmission lines, the power supply has to be low noise and fast reacting, etc pp.

From the description of your photodiodes, especially as you call them photomultipliers, I guess they are actually avalanche photodiodes. There is a large corpus of material on how to reduce their noise. Probably the biggest contributor after temperature is power supply noise. One thing that your simple circuit cannot really do is, keeping the current through the diode constant. Your -30V would have to be really low noise to ensure that your current is stable. Unfortunately, most voltage regulators, especially negative regulators are very noisy. You would do better in redesigning the supply to be a current source instead. This way the amplification (and thus the time it takes to form an avalanche in the diode) can be kept more constant. If this is not enough, you can use a differential circuit, where you emulate the APD by a capacitor of the right size, and thus can subtract the supply noise (this will not reduce the noise due to amplification modulation, though). Also, as peufeu wrote, you want to have one supply per APD. If they are shared, you will inevitably get cross coupling effects. This also includes parallel wires and magnetic coupling! Also keep in mind that APDs are fast switching circuits. You have to treat them like RF devices.

The opamp you have chosen is quite decent, but it has a relatively high 1/f corner frequency of around 10kHz. Unless you really need the high GBW, I would suggest to choose one that is slower, but also has a lower 1/f noise corner frequency. As mentioned above, you do not really care about slew rate, as long as the repetition rate is low. Though, if your slew rate is low, you need to keep it as constant as possible, to keep timing stable. This means that your circuit should be in a temperature stable environment. For your requirement of a few 100ps, an office environment should be sufficiently stable in terms of temperature.

For low noise applications, choose opamps from Analog or Linear. TI, even though cheaper, does not even come close in the performance and quite often their opamps perform worse in real circuits than their datasheets would suggest. Finding the right opamp is quite a bit of work and can easily take a few days to screen all candidates and sort them by their characteristics. The capacitors you have for the opamp are insufficient for the fast opamps you are using. You should use some 10n with a high resonant frequency (that means also as small case as possible) as close as possible to the opamp, followed by 100n and 1u. Do not go leave out the 100n or use 6.8u instead of the 1u. Each capacitor size has its own resonant frequency. If the steps between the sizes are too large, you will build an L-C resonator out of two capacitors. I would not fret too much about decoupling both opamps. Unless your power supply is badly designed you should not see any voltage droop. Putting resistors into the supply lines does theoretically help to decouple, but in practice you can make performance quite a bit worse than by just plain connection. Good capacitor decoupling, with the above mentioned stacking, is important, but anything beyond that should be only done if you have probably cause to believe that supply coupling is indeed the cause of the problems you see (most likely it is not).

As for output amplification, your multiple amplifier stages approach is probably the best. This way you can improve the slew rate step by step without introducing too much noise/jitter. This approach and how to properly design each stage has been documented by Collins. I would not use any external amplifier module as you currently do, as they are not well adapted to your needs. Instead use appropriate opamps or build discrete amplifiers.

One thing that you have not mentioned at all and that affects the performance of the circuit a lot is power supply noise. You need to get to as little noise as possible, as all the power supply noise in the opamps modulate their amplification and thus their slew rate and delay. I recommend using the LT3042 as they have an incredible low noise. There is also a higher current and a negative voltage variant of those, if you need. Before using them, you should read the appnotes carefully. The specs of the LT3042 LDOs is so incredibly good that it's easy to screw them by applying normal good design practices.

Answer 3

Are your layouts identical ? Are the VDD bypass caps identical? You need substantial Idd, and mismatched power rail impedances will upset the opamp timing. Experiment with dampening the +5V and the -5V rails, using 2 caps in parallel on each rail for each opamp (e.g. EIGHT capacitors of size 0.01uF for the 2 opamps and the 2 rails). In each of the 4 pairs of caps, insert a 1 Ohm Rdampen in 4 places. Dampening is computed as sqrt(L / C); 10nH and 10nF needs 1 ohm Rdampen.

Are your opamp VDD isolated from each other? Install 1--10 ohm resistors from the global power to the local VDDs (4 resistors), and place the resistors right by the opamps. Remember the high frequency PSRR is approximately ZERO. You must provide very clean power to each opamp, and keep them isolated if you want to trust the timing.

^{simulate this circuit – Schematic created using CircuitLab}

Now examine the PSRR curves of the OPA656

This plot does not provide any information out at 1GHz. The trend lines suggest the OpAmp cannot reject trash out at 1GHz. Thus YOU have to design, in the schematic, the filtering and dampening to provide quiet non-ringing power.

Answer 4

I would choose multiple TIA's cascaded specially design to yield greater gain bandwidth resistance or better look at Silicon on Insulator SOI, integration with photo detectors that promises reduced L,C values and ZBW values greater than 30GHz in many R&D areas.

\$ZBW ≈ R_f*BW_{TIA}≈\dfrac{A}{C_{CinT}}\$

Ref: https://www.intechopen.com/books/photodiodes-from-fundamentals-to-applications/design-of-multi-gb-s-monolithically-integrated-photodiodes-and-multi-stage-transimpedance-amplifiers#

Potential sources: http://www.poet-technologies.com/ ( but not likely)

also

• Have you considered LMH6629 ? –3dB BW of 900 MHz and 1600 V/µs slew rate
  • Supply Voltage Range 2.7 V to 5.5 V
  • Then add a differential amplifier 500 ohm load with 20mA emitter current source and 50 ohm collector load for 20dB more gain. http://www.ti.com/lit/ds/symlink/lmh6629.pdf
  • ultimately you want a rise time < 500ps with ultra low noise and high gain with low input capacitance then get a rise time differential 10% of this.
  • then only use SMA semi-rigid coax to target.

Answer 5

You absolutely must have the detectors and amplifiers on separate board, otherwise too much high freq coupling.

25 ohm is really too low for the feedback: the output of the opamp may struggle to drive it properly. You can instead use 10..25 ohm current sense resistor followed by low noise voltage amplifier like THS4303.

One can also use RF transformer, or simply 50ohm resistor to match the output of the SiPm to 50 ohm and then use some standard 50 ohm amplifiers ( even AC coupled).